外文翻譯PWM整流器中的應(yīng)用自反饋串級(jí)調(diào)速系統(tǒng)..

1、固中原工學(xué)院這息裔勢(shì)學(xué)隔畢業(yè)論文（設(shè)計(jì)）外文翻譯題 目：PWM整流器中的應(yīng)用自反饋串級(jí)調(diào)速系統(tǒng)系部名稱：專業(yè)班級(jí)：學(xué)生姓名：學(xué) 號(hào)：指導(dǎo)教師：教師職稱：20年月曰PWM整流器在自反饋串級(jí)調(diào)速系統(tǒng)的應(yīng)用摘要：本文分析了自反饋串級(jí)調(diào)速系統(tǒng)功率因數(shù)較低的原因，并提出了一種新的基于PWM技術(shù)的串級(jí)調(diào)速系統(tǒng)方案。在此系統(tǒng)中，用IGBT代替了可控硅。它可以提供電容式無(wú)功功率去補(bǔ)償傳統(tǒng)的串級(jí)調(diào)速系統(tǒng)產(chǎn)生的感應(yīng)無(wú)功功率，因此，它可以提高功率因數(shù)。文 中介紹了 PWM整流器和PWM電流控制方案。最后給出了仿真結(jié)果和結(jié)論，結(jié)果表明， 新系統(tǒng)工作在單位功率因數(shù)。索引詞-串級(jí)控制，功率因數(shù)，脈寬調(diào)制一導(dǎo)言在我們的日常

2、生活和工業(yè)生產(chǎn)中，電力系統(tǒng)占相當(dāng)大的比重，特別是這些載荷鼓風(fēng) 機(jī)和泵，使用多能量，因此節(jié)能的風(fēng)機(jī)和水泵正在成為工業(yè)生產(chǎn)的主要問(wèn)題之一。利用 可控硅串級(jí)調(diào)速控制，是風(fēng)機(jī)和水泵節(jié)能的有效手段。比較變頻調(diào)速控制，這種方法更 好，更便宜，不僅能平滑調(diào)速還能節(jié)能 20%? 40%。但是，傳統(tǒng)的級(jí)聯(lián)速度控制系統(tǒng)具 有低諧波因素和多一些缺點(diǎn)。功率因數(shù)高負(fù)荷，高速低轉(zhuǎn)速負(fù)荷0.4 0.6。它帶來(lái)了巨大的浪費(fèi)和污染。這個(gè)缺點(diǎn)阻礙了延伸和串級(jí)調(diào)速中的應(yīng)用。在一種新的級(jí)聯(lián)速度控制系 統(tǒng)方案的基礎(chǔ)上，提出了 PWM整流器。在新的計(jì)劃中，晶閘管逆變器被IGBT代帶，并 且系統(tǒng)具有高功率因數(shù)。二CHOP內(nèi)饋調(diào)速的原理在電

3、機(jī)中內(nèi)反饋串級(jí)調(diào)速控制系統(tǒng)是異步電動(dòng)機(jī)轉(zhuǎn)子系列woundrotor抵抗速度的基礎(chǔ)。一個(gè)新的三相對(duì)稱繞組命名調(diào)整繞組定子繞組上，建立的初級(jí)繞組稱為主繞組。額 外的電動(dòng)勢(shì)繞組的調(diào)整是由主繞組引起的。采用晶閘管逆變器，附加電動(dòng)勢(shì)serriedwound與轉(zhuǎn)子繞組，其速度可以通過(guò)改變其規(guī)定。普通串級(jí)調(diào)速系統(tǒng)調(diào)速是通過(guò)改變反角B,但無(wú)功功率提升，功率因數(shù)作為反角增加而減少。因此，斬波串級(jí)speedregulation系統(tǒng)如下：1. 對(duì)斬波串級(jí)調(diào)速系統(tǒng)中的整流橋輸出電壓Ud=2.34sE20。逆變器的輸出電壓fyT -TUi =2.34Ut2COS：轉(zhuǎn)子回路方程是 Ud二 Ui。因此，旋轉(zhuǎn)速度公式可以顯示

4、為:Ut2是調(diào)整相繞組電壓，是斬波器脈沖持續(xù)時(shí)間比和對(duì)應(yīng)E20T功率因數(shù)的分析的n 1 Ut2COS0（T）n I 對(duì)串級(jí)調(diào)速系統(tǒng)功率因數(shù)為： COSB =； T在公式中，P1是由電機(jī)J(RR ) +(Qi+Qt)吸收的有功功率；PT是有功功率給電網(wǎng)的反饋；Q1是由電機(jī)從電網(wǎng)吸收的無(wú)功功率；QT 是逆變器從電網(wǎng)吸收的無(wú)功功率。在斬波串級(jí)調(diào)速系統(tǒng)，逆角B為固定的，因?yàn)?，它是一般約30。因此，在系統(tǒng)中QT是不變的。但是，當(dāng)電機(jī)在低速運(yùn)行，P增加，功率因數(shù)下降。四PWM整流器的定性分析可控硅由PWM整流器 取代，新的級(jí)聯(lián)速度控制系統(tǒng)方案原理圖圖 2:（圖5）所以一定要確保輸出端的直流電壓,恒定的情況

5、下工作，因此Qt =0或Qt = -Qi可以提高功率因數(shù)。PWM整流器是一個(gè)四象限變流器。其交流和直流側(cè)可以控制的。當(dāng)使用電網(wǎng)電測(cè)力矢量為參考，則PWM整流器的工作fourquadrant可以通過(guò)控制交流側(cè)電壓向量 V。I是固定的，所以V=bLI也是固定的。在這種情況下，在 PWM整流器交流側(cè)電壓矢量的 運(yùn)動(dòng)軌跡是一個(gè)圓的半徑的 VL。當(dāng)V的電壓矢量端點(diǎn)的圓軌跡 A點(diǎn)，電流矢量延遲電 動(dòng)勢(shì)矢量E900 。PWM整流器網(wǎng)側(cè)電感為圖3顯示的特征。當(dāng)V的電壓矢量端點(diǎn)的圓軌 跡B點(diǎn)，電流矢量I是平行，與電動(dòng)勢(shì)矢量 E同一方向。在PWM整流器網(wǎng)側(cè)圖4顯示 為阻力特性。當(dāng)電壓矢量端點(diǎn)的圓 V位點(diǎn)C點(diǎn)，電流

6、矢量I是電動(dòng)勢(shì)矢量E900的PWM 整流器網(wǎng)側(cè)電容，圖5顯示的特征。當(dāng)V的電壓矢量端點(diǎn)的圓軌跡 D點(diǎn)，電流矢量I是 平行，與電動(dòng)勢(shì)矢量E相反的方向。在PWM整流器網(wǎng)側(cè)顯示為圖6負(fù)阻特性。B（圖6）輸入電流和交流側(cè)電壓可以 在負(fù)阻或電容特性五PWM整流器控制系統(tǒng)的設(shè)計(jì)三相PWM整流器交流側(cè)均為時(shí)變交流量，不利于控制系統(tǒng)設(shè)計(jì)。引進(jìn)電機(jī)矢量控制的思想，從交流側(cè)看可以把電感電阻和交流側(cè)看成一個(gè)交流電機(jī)的模型與三相逆變器相同，我們更可以把三相交流電機(jī)的控制理論運(yùn)用到三相PWM整流器中。把三相靜止坐標(biāo)變換成二相旋轉(zhuǎn)坐標(biāo)，在進(jìn)行解耦控制，電壓為外環(huán)，電壓給定和實(shí)際的差值進(jìn)行 調(diào)節(jié)后經(jīng)過(guò)PI后得到有功電流的給

7、定，設(shè)定想要給定的無(wú)功電流，高功率因數(shù)系統(tǒng)中, 功率因數(shù)為1,所以無(wú)功電流給定為0,在通過(guò)檢測(cè)出來(lái)的實(shí)際的電流矢量變換和解耦后得到的實(shí)際的有功電流和無(wú)功電流與給定的有功電流和無(wú)功電流的比較來(lái)得到指令電壓 信號(hào)，從而我們得到如圖所示的控制框圖來(lái)實(shí)現(xiàn)系統(tǒng)的控制。這種直接通過(guò)檢測(cè)實(shí)際電 流，再進(jìn)行矢量變換解耦控制的方法直接對(duì)電流進(jìn)行控制和上述的通過(guò)電壓的關(guān)系來(lái)間接控制電流的方法更客觀，而且控制更有效。因此根據(jù)坐標(biāo)變換的關(guān)系，三相PWM整流器拓?fù)浣Y(jié)構(gòu)的兩相旋轉(zhuǎn)坐標(biāo)系 dq模型可描述為：Lp R - LidVdIL 吐Lp R iqVq上述方程中，ed， eq是d和q軸的電動(dòng)勢(shì)矢量，矢量Vd ,Vq是組

8、件d和q軸的在AC端，電壓矢量分量，id， iq是在交流側(cè)電流向量d和q軸分量，p為微分算子。在公式（2），因?yàn)镈和q軸分量耦合，很難設(shè)計(jì)出控制系統(tǒng)。因此，一個(gè)控制策略 的前饋解耦是給出的。PI調(diào)節(jié)器，是層狀的電流調(diào)節(jié)器，所以控制方程，矢量量化為：q _iq _Lid eq（ 3）+ 0iPSid id Liqediq，id 等價(jià)于 iq，id。Kip， Kii是比例調(diào)節(jié)系數(shù)和積分調(diào)節(jié)回路的電流調(diào)節(jié)系數(shù)。在電壓環(huán)，所需的電流是三相對(duì)稱正弦電流，它的電網(wǎng)電壓同頻。因此，在同步旋轉(zhuǎn)坐標(biāo)系 中，iq，id是DC數(shù)量。因此，iq和id可以順利地調(diào)整PI調(diào)節(jié)器。方程式（4）iq丄 KiP “ Vdc-V

9、dc（ 4）I S丿介紹了在dq概念的瞬時(shí)功率，同步旋轉(zhuǎn)坐標(biāo)系，瞬時(shí)有功功率和PWM整流器無(wú)功功率可以顯示為（5）:為了補(bǔ)償電機(jī)吸收無(wú)功功率,PWM整流器工程電容性質(zhì)。因此，編號(hào)是:ideq表格方程（3）（4）（6），對(duì)PWM整流器控制框圖圖7：（圖7）六PWM整流器串級(jí)調(diào)速系統(tǒng)的仿真結(jié)果PWM整流器仿真串級(jí)調(diào)速控制的結(jié)構(gòu)圖和圖 7的直接電流控制策略系統(tǒng)的基礎(chǔ)。模 擬參數(shù)是電機(jī)額定功率為710kW，定子額定電壓為6000V,額定電流為72A條，調(diào)整電 壓為510V，額定轉(zhuǎn)速1487r/min。交流側(cè)電感為0.001H，直流側(cè)為0.0033F電容，直流 電壓為1200V的。仿真結(jié)果圖8,圖9和圖

10、10。（圖8）從圖8可以看出直流電壓為1200V，它有利于順利調(diào)節(jié)速度。圖 9為A相電壓和 PWM整流器交流側(cè)電流。結(jié)果表明，PWM整流器的電容特性運(yùn)行。因此，有源電力輸 送到電網(wǎng)，同時(shí)產(chǎn)生的容性無(wú)功功率。因此，系統(tǒng)的工作原理功率因數(shù)，電壓波形和電 流如圖10。在傳統(tǒng)的斬波串級(jí)調(diào)速系統(tǒng)，因?yàn)榫чl管半控裝置，逆變器上運(yùn)行的特點(diǎn)和電感電流的波形不是正弦波。因此網(wǎng)側(cè)電流延遲和系統(tǒng)的功率因數(shù)。電流和電壓 晶閘管逆變器并網(wǎng)如圖11圖12所示。除了新的串級(jí)調(diào)速控制系統(tǒng)具有諧波少得多。 從圖13和圖14,總諧波失真的新系統(tǒng)(THD )是5.56%，是對(duì)傳統(tǒng)的斬波串級(jí)調(diào)速系統(tǒng)，以12.28%的一半aev a

11、az qubs qwo.wo.es q.w q-bTjm（圖 11）D.B1 O.aa O_B3 O.M OJDB a OB OJB-7 OlBO OL0D 0.0 nmo（圖 12）Furdamental （5aNz） = 03 32 , rHEJ= 5.55%_ 5E5 4E5 S? 2XIV:1oS B 7 a 9 ID 11 12 13 HiuicrtiL ordui（圖 13） |（圖 14）七結(jié)論本文提出了一種新的以級(jí)聯(lián)速度控制系統(tǒng)為基礎(chǔ)的PWM整流器。仿真驗(yàn)證了新的控制系統(tǒng)，新系統(tǒng)可以工作在單位功率因數(shù)。與傳統(tǒng)的斬波串級(jí)調(diào)速系統(tǒng)相比，新的串 級(jí)調(diào)速控制系統(tǒng)可節(jié)省無(wú)功補(bǔ)償裝置，降低

12、諧波。因此，PWM整流器串級(jí)調(diào)速系統(tǒng)將廣泛應(yīng)用于未來(lái)。八參考文獻(xiàn)1 馬里烏什馬林諾夫斯基，馬立克 Jasinski,簡(jiǎn)單的三相PWM整流器直接功率控制采 用空間矢量調(diào)制（DPC的支持向量機(jī)），工業(yè)電子，第一卷電機(jī)及電子學(xué)工程師聯(lián)合會(huì)交 易, 51, 2 號(hào)，2004 年 4 月。2 蔣優(yōu)化，寧宇，和龔優(yōu)岷，研究單位功率因數(shù)的內(nèi)饋斬波級(jí)聯(lián)調(diào)速系統(tǒng) ”，電力電子,第39卷第6號(hào)，2005年12月。3 章充維，張星，“PWMg流器及其控制策略”，北京：中國(guó)機(jī)械工業(yè)出版社，2003。4 陳白石 電力拖動(dòng)自動(dòng)控制系統(tǒng)”，北京：中國(guó)機(jī)械工業(yè)出版社，1997年論文5 宋桂英，內(nèi)反饋調(diào)速電機(jī)系統(tǒng)”，碩士論文，

13、河北科技大學(xué)。九履歷馬暢瀟出生在1982年9月18日的中國(guó)。他于2005年加入中國(guó)北方電力大學(xué)?，F(xiàn)在，他 正在攻讀電氣和電子工程學(xué)院學(xué)士學(xué)位和他的專業(yè)是電力電子及電氣傳動(dòng)設(shè)備。電子郵 箱: machangxiao汪埃甍于1963年出生在中國(guó)。她是一名華中電力大學(xué)的副教授。是美國(guó)威斯康星大學(xué)麥 迪遜分校學(xué)者從2006年1月至Jun.2007。電子郵箱：aiming_068本文摘譯自： R.Pe na.J.C.Ctare.GM.Asher.Doubly fed in duct ion gen erator using back-to back PWM conv erters and its app

14、licati on to variable-speed wind en ergy cratio n.lEEEProc-Electr.PowerAppl.Voi.143.NO.3.May1996:231-241The Application of PWM Rectifier Used in SelfFeedbackCascade Speed Control SystemMa Changxiao and Wang AimengAbstract-Analyzed the reason that the power factor of self feedback cascadespeed contro

15、l system is poor. A new cascaded speed-adjusting system scheme based on PWM tech nique is proposed in this paper. SCR is substituted with IGBT in the system. It can provide capacitive reactive power to compensate inductive reactive power which the conventional cascaded speed adjusti ng system produc

16、es. So it can improve power factor. PWM rectifier and PWM direct curre nt con trol strategy are in troduced in the paper. At last, simulati on result and con clusi on are give n. It shows that the new system works at un ity power Factor.Index Terms- Cascade control, power factor, PWMI. INTRODUCTIONI

17、N our daily life and in dustrial producti on, electric drive acco unts for a large proporti on, especially these loads air blowers and pumps that use much en ergy, so the en ergy sav ing of fans and pumps is beco ming one of the mai n issues in in dustry producti on. The use of SCR cascadespeed con

18、trol is an effective means of the en ergy con servati on of fans and pumps. Compare with frequency control of motor speed, this method is better and cheaper,and not only bring about smooth speed regulating but also save energy 20%40%. But the conven ti onal cascaded speed con trol system has some di

19、sadva ntages of low factor and much harm onic. The power factor is 0.6 with high-speed load and 0.4 with low-speed load. It brings great waste and pollution to the power. This disadvantage obstructs the extension and applicati on of cascade speed regulati on. A new cascaded speed con trol system sch

20、eme based on PWM rectifier is proposed in this paper. In the new scheme, thyristor inverter is substituted with IGBT, and the system works with high power factor.II. PRINCIPLE OF CHOP INNER FEEDBACK SPEED REGULATIONCascade speed con trol system with in ternal feedback is base on the theory of rotor

21、series resista nee speed of woun drotor in ducti on motor. I n the motor, a new three-phase symmetrical winding n amed adjusti ng winding is foun ded on the stator winding and the primary winding called main winding. The additi onal electromotive force is provided by adjusti ng winding which in duce

22、d from main wi nding. Using thyristor inv erter, the additi onal electromotive force is serriedwo und with rotor winding, and the speed can be regulated by cha nging it. The speedregulation in ordinary cascadespeed control system is by changing the inverse angle B , however the reactive power enhan

23、ced and the power factor decreased as the in crease of inv erse an gle. So chopp ing cascade speedregulati on system is proposed. The system prin ciple diagramis Fig.1.Fig.1So the formula of the rotation speed can shows an:= n0 1Ut2cosE(Ti 亍E20TFig. 1. Structure of chopping cascade speed regulation

24、systemOutput voltage of the rectifier bridge is Ud =2.34sE2.Output voltage of the inverter isU2.34U T2 cos :|UiEquation of the rotor loop is U dU l 2 is the phase voltage of the adjusting winding, is the pse duration ratio of the chopper and E20 is rotor rated voltage. So the rotati on speed of the

25、motor can be con trolled by regulat ing the pulse durati on ratio. R_FT,巳 _ PT 2Q1 Qt 2III. ANALYSE OF POWER FACTORThe power factor of cascade speed con trol system isos9In the equation, P1 is the active power absorbed from grid by motqrPT is the active power feedback to grid form the system; Q1 is

26、the in ductive reactive power which is absorbed by motor from grid; QT is the in ductive reactive power absorbed from grid by inv erter. I n the chopping cascade speed regulation system, the inverse angle is fixed, because of the margin, it is gen erally about 300. So QT is cha ngeless in the system

27、. But whe n the motor runs at a low speed, PT in creased, and the power factor decreased.IV. ANALYSE OF PWM RECTIFIERSubstituted SCR by PWM rectifier, the principle diagram of the new cascadedspeed con trol system scheme is Fig.2.The Application of PWM Rectifier Used in Self- Feedback Cascade Speed

28、Control System Ma Changxiao and Wang Aimeng Fig. 2. Structure of PWM rectifier cascadespeed regulati on system PWM rectifier is a four-quadra nt con verter. Its AC and DC sides can be con trolled. When using the grid electromotive force vector as refere nee, the PWM rectifier can work in fourquadran

29、t by controlling the AC side voltage vector V . I hypothesis fixedness, so the VL =L I is fixedness too. In this situation, the motion trajectory of the PWM rectifier AC side voltage vector is a round with the radius of VL . When the endpoint of voltage vector V on the circle locus A point, current

30、vector I delays electromotive force vector E900 and the net side of the PWM rectifier shows in ducta nee characteristic as Fig.3. Whe n the en dpo int of voltage vector V on the circle locus B point, curre nt vector I is parallel and the same direct ion with electromotive force vector E . The net si

31、de of the PWM rectifier shows positive resista nee characteristic as Fig.4. When the endpoint of voltage vector V on the circle locus C point, current vector I is lead electromotive force vector E90and the net side of the PWM rectifier shows capacita nee characteristic as Fig.5. When the en dpo int

32、of voltage vector V on the circle locus D point, curre nt vector I is parallel and the opposite directi on with electromotive force vector E . The net side of the PWM rectifier shows negative resistance characteristic as Fig.6.AVEDSo make sure the output voltage of the DC side isinv ariable ness, th

33、e in put curre nt and voltage of the AC side can work on n egative resista nee or capacita nee characteristic, hence QT =0or QT=- Q1 . The power factor is in creased.V. DESIGN OF THE PWM RECTIFIER CONTROL SYSTEMAs the AC side of three-phase PWM rectifier is timevarying, it is difficulty to design th

34、e con trol system. So the method of vector con trol of asyn chro nous motor is in troduced. The ABC referenee frame changes to d-q synchronously rotating referenee frame bases on the grid voltage frequency. So the sinusoidal variables in ABC reference frame become DC variables in d-q syn chro no usl

35、y rotat ing refere nce frame. It is easy to desig n the con trol system .In the d-q synchronously rotating reference frame, the q coordinate axis is coincides with the grid electromotive force vector Edq , so the d axis comp onent of the electromotive force vector ed is zero .In the synchrono usly r

36、otat ing refere nce frame, the q axis comp onent shows the active power and the d axis shows the reactive power. In d-q synchronously rotating reference frame, the model of three-phase PWM rectifier is:_eq卜+R割和+卜（2）-國(guó)LLp + Riq斗In the equati on men ti oned above, ed ,eq is the d and q axis comp onent

37、 of the electromotive force vector Edq , vd ,vq is the d and q axis comp onent of the voltage vector in the AC side, id ,iq is the d and q axis component of the current vector in the AC side, and p is the differential operator. In the equation (2), because the d and q axis component is coupled, it i

38、s difficult to design the control system. So a control strategy based on the feed-forward decoupling isapplied. The PI regulator is bedded in the current regulators, so the control equati on of vd ,vq is:Ksvd* id-id 5 edKiP,KiI is the proportion adjustment coefficient and the integral regulation coe

39、fficient ofthe curre nt regulati ng loop. *, * iq id is the appo in ted value of iq ,id .In the voltage loop, theneeded current is the three phassymmetrical sine current, and it s the same frequency of gri(voltage. So in d-q synchronously rotating referenee frame,iq andid are DC quantity. Hence iqan

40、d id can be adjusted smoothly by PI regulator. The equation is (4).KiPdc (4)Introduced the conception of instantaneous power, in the dq synchronously rotating refere nee frame, the in sta ntan eous active power and reactive power of the PWM rectifier net side can shows as (5):q piq -eqed(5)In order

41、to compensate the inductive reactive power absorbed by motor, the PWM rectifier works in capacitive character. So id is:Form the equation (6), the control block diagram of PWM rectifier is Fig.7.VI. SIMULATION RESULTS OF THE PWM RECTIFIER CASCADESPEED CONTROL SYSTEMSimulate the PWM rectifier cascade

42、 speed control system base on the structure of Fig.1 and the direct current control strategy of Fig.7. The simulation parameters are: the rated power of inner-feeding motor is 710kW, the stator rated voltage is 6000ythe rated current is 72A, the voltage of adjusting winding is 510V, the rated speed

43、is 1487r/min. The inductance in AC side is 0.001H, the capacitancein DC side is0.0033F, the DC voltage is 1200V. The results of simulation are Fig.8, Fig.9 and Fig.10.Fig.9Fig.10From Fig.8, the DC voltage works on 1200V, it is beneficial to regulate the speed smoothly. Fig.9 is the A phase voltage a

44、nd current of PWM rectifier AC side. It shows that PWM rectifier runs on capacitanee characteristic. So it transports active power to the grid mea nwhile produces capacitive reactive power. Hence the system works on un ity power factor, as the waveform of voltage and current in Fig.10.In conventiona

45、l chopping cascade speed regulation system, because thyristor is half-c on trolled device, the inv erter runs on in ducta nee characteristic and the curre nt waveform is not sine wave. Hence current delays voltage in net side and the power factor of the system is poor. The current and voltage of thy

46、ristor-inverter and grid is shown in Fig.11 and Fig.12o.b ae-i ass? 口8 qbidjk asr 09 gr aThitiqFig.113OlSI OlS2 QlB3 O.B4 O.K Q.W DJB7 OlBO OlBD OJQTimoFig.12Besides the new cascade speed con trol system has much less harm onic. From Fig.13 andFig.14, the total harmonic distortion (THD) of the new s

47、ystem is 5.56%, it is about half of the conven ti onal chopp ing cascade speed regulati on system which is 12.28%.Furdainental 50Hz) = Q3 32 , THD= 5 5E%s*hU 12345 B 79 B IO 1112 13Harmonic ardlerFig.13Fig.14VII. CONCLUSIONThis paper proposed a new cascaded speed control system scheme based on PWM rectifier. The simulation verified the analysis of new control system that the new system can work in